Interference suppression with mitigation of intermodulation distortion

ABSTRACT

A method of interference suppression with intermodulation distortion mitigation includes processing an RF signal comprising an RF signal of interest and an RF interfering signal to produce a first and second RF drive signal each with a desired RF interference signal power and having a 90 degree relative phase. The first RF drive signal is imposed onto a first optical signal with a modulator to generate a first modulated optical signal so that the modulator has a large-signal behavior that is characterized by a Bessel function of the first kind J 1 (ϕ), wherein the desired power at a frequency of the interference signal of the first drive signal is chosen to correspond to a zero of the Bessel function of the first kind J 1 (ϕ). The second RF drive signal is imposed onto a second optical signal with a modulator to generate a second modulated optical signal so that the modulator has a large-signal behavior that is characterized by a Bessel function of the first kind J 1 (ϕ), wherein the desired power at a frequency of the interference signal of the second drive signal is chosen to correspond to another zero of the Bessel function of the first kind J1(ϕ). The first and second modulated optical signal are combined with an optical power ratio that is selected to suppress third-order intermodulation distortion products in an electrical signal generated by detecting the optically combined first and second modulated optical signals.

CROSS REFERENCE TO RELATED APPLICATION

The present application is a non-provisional application of U.S.Provisional Patent Application No. 62/868,208, filed on Jun. 28, 2019,entitled “Interference Suppression with Mitigation of IntermodulationDistortion”. The entire contents of U.S. Provisional Patent ApplicationNo. 62/868,208 are herein incorporated by reference.

INTRODUCTION

A known problem with many RF systems is the challenge of receivinglow-power signals in the presence of interference from otherhigher-power signals. The powers and frequencies of both the desiredsignals and the undesired (interference) signals can cover a wide rangeof values for many practical applications. It is therefore highlydesirable to suppress interference signals over a wide dynamic range ofinterference signal powers, as well as to suppress interference over awide RF bandwidth.

Photonic systems have been used to improve the reception of low-powersignals in the presence of significant interference. In these systems,the RF signals, including both desired and undesired signals, areimposed on an optical signal using an optical modulator. The modulatedoptical signal is then received at a photodetector to convert the signalback to an electronic signal. While various photonic architectures havebeen explored to provide RF signal cancellation and suppression usingphotonic approaches, improvements are still needed to realize systemswith better performance, such as broader bandwidth and improved varioussignal fidelity measures.

BRIEF DESCRIPTION OF THE DRAWINGS

The present teaching, in accordance with preferred and exemplaryembodiments, together with further advantages thereof, is moreparticularly described in the following detailed description, taken inconjunction with the accompanying drawings. The skilled person in theart will understand that the drawings, described below, are forillustration purposes only. The drawings are not necessarily to scale,emphasis instead generally being placed upon illustrating principles ofthe teaching. The drawings are not intended to limit the scope of theApplicant's teaching in any way.

FIG. 1A illustrates a Mach-Zehnder modulator-based link architecturethat suppresses a high-power input signal at one frequency f_(INT) whilepreserving a low-power input signal at a second frequency f_(SOI).

FIG. 1B illustrates a plot showing the output signal power as a functionof input signal power for a fiber-optic link that uses the Mach-Zehnderinterferometric modulator link architecture of FIG. 1A.

FIG. 1C shows a graph of the measured performance of a known techniqueof suppression of RF interference.

FIG. 2 illustrates an embodiment of a Mach-Zehnder modulator link usinga nonlinear function modification (NLFM) system of the present teaching.

FIG. 3 illustrates a graph showing measured results from an experimentto verify the nonlinear function modification capability of thearchitecture described in connection with FIG. 2.

DESCRIPTION OF VARIOUS EMBODIMENTS

The present teaching will now be described in more detail with referenceto exemplary embodiments thereof as shown in the accompanying drawings.While the present teaching is described in conjunction with variousembodiments and examples, it is not intended that the present teachingbe limited to such embodiments. On the contrary, the present teachingencompasses various alternatives, modifications and equivalents, as willbe appreciated by those of skill in the art. Those of ordinary skill inthe art having access to the teaching herein will recognize additionalimplementations, modifications, and embodiments, as well as other fieldsof use, which are within the scope of the present disclosure asdescribed herein.

Reference in the specification to “one embodiment” or “an embodiment”means that a particular feature, structure, or characteristic describedin connection with the embodiment is included in at least one embodimentof the teaching. The appearances of the phrase “in one embodiment” invarious places in the specification are not necessarily all referring tothe same embodiment.

It should be understood that the individual steps of the method of thepresent teaching can be performed in any order and/or simultaneously aslong as the teaching remains operable. Furthermore, it should beunderstood that the apparatus and method of the present teaching caninclude any number or all of the described embodiments as long as theteaching remains operable.

Designers of RF systems sometimes desire the ability to receivelow-power signals of interest, for example with antennas in the presenceof one or more signals of sufficiently high-power that interferes withreception of low-power signals of interest. Designers of RF systems alsosometimes desire the ability to separate low-power signals of interest,for example, in an electronic processing system from anotherhigher-power signal that is present at the same point in the electronicprocessing system and interferes with the low-power signals of interest.One of the challenges to designing a system in which high-power signalsare simultaneously present with low-power signals is the extent over,and degree to, which the system response function is linear.

The response function of a system will saturate when the signal power ishigher than a certain threshold saturation input power. That is, thesystem response function will be a constant value for any power greaterthan the threshold saturation input power. When the system responsefunction is in saturation, the presence of the low-power signals iscompletely masked. The threshold saturation power can be increased byusing certain circuit topologies and operating conditions. For example,increasing the power supply voltage alone will increase the saturationpower.

For moderately high-power signals, which have powers that are less thanthe saturation threshold but, greater than the power for which theresponse is sufficiently linear, these moderately high-power signals canstill significantly interfere with the ability of the system to receivethe low-power signal. Various linearization techniques can be used toimprove the degree to which the system response function is linear. Insome cases these linearization techniques are sufficient to enable thesystem to receive the low-power signal.

Improved circuit topologies and operating conditions, and the use oflinearization techniques are all aimed at making the system responsefunction more closely approximate the ideal, which is a function that isperfectly linear over an infinite range of powers. While thesetechniques can assist in the receiving of a low-power signal in thepresence of higher power signals, new approaches are needed to providebetter performance.

Recently work has been reported on a new approach to receive low-powersignals in the presence of higher-power signals. This approach tries toexploit, rather than linearize, a nonlinear response to enable alow-power signal to be received in the presence of a high-power signal.More than one set of researchers has demonstrated that the inherentlysinusoidal nonlinearity of a Mach-Zehnder electro-optic modulator can beleveraged to suppress a high-power interfering signal whilesimultaneously recovering a lower-power signal of interest. See, forexample, V. Urick, J. Diehl, J. McKinney, J. Singley, and C. Sunderman,“Nonlinear optical angle modulation for suppression of RF interference,”IEEE Trans. Microwave Theory Tech., vol. 64, ppl 2198-2204, July 2016.Also see W. Loh, S. Yegnanarayanan, R. Ram, and P. Juodawlkis, “Anonlinear optoelectronic filter for electronic signal processing,”Scientific Reports. When the voltage of the interfering signal imposesoptical phase modulation ϕ_(INT) in each arm of the Mach-Zehnderinterferometer to a degree that corresponds to a zero of J₁(ϕ_(INT)),where J_(1n)(ϕ) is the n^(th)-order Bessel function of the first kind,the resulting photocurrent in a detector connected to the output of themodulator is zero at the power level of the interfering signal. Thephotocurrent is not zero at the power level of a signal of interest thatimposes a smaller modulation phase ϕ_(SOI) for which J₁(ϕ_(SOI))≠0. Thislarge-signal, high-power Mach-Zehnder transfer function will bedescribed further herein.

However, an undesirable side-effect of this approach is its generationof third-order intermodulation distortion at twice the interfererfrequency±the signal-of-interest frequency. The output power at thisintermodulation distortion frequency is, unfortunately, exactly equal tothe output power at the signal of interest because the photocurrents atthese frequencies are proportional to J₂(ϕ_(INT)), and J₀(ϕ_(INT)),respectively, and because J_(n+1)(ϕ)=−J_(n−1)(ϕ) at all zeroes ofJ_(n)(ϕ). Hence this technique resolves one issue, the suppression ofthe high-power signal, but at the cost of creating a new issue, thegeneration of intermodulation distortion of the same magnitude as thelow-power signal.

Techniques for linearizing the system response function can be used toreduce the third-order intermodulation distortion. However,linearization would also significantly reduce or eliminate thesuppression of the high-power signal, which is a direct result of thenonlinear transfer function.

The present teaching overcomes many of the shortcomings of knowntechniques that attempt to receive low-power signals in the presence ofhigher-power signals. Various aspects of the methods and systems of thepresent teaching relate to modifying the nonlinear function of thesystem so as to change one or more particular terms in the function,while otherwise leaving the nonlinear function intact. Such techniquesare referred to herein as Nonlinear Function Modification (NLFM). Oneaspect of the present teaching is applying nonlinear functionmodification according to the present teaching to suppress the stronginterferer while simultaneously recovering a lower-power signal ofinterest and also while simultaneously suppressing the strongintermodulation distortion product that is generated at a frequency oftwice the interferer frequency±the signal-of-interest frequency.

FIG. 1A illustrates a Mach-Zehnder modulator-based link architecture 100that suppresses a high-power input signal at one frequency f_(INT) whilepreserving a low-power input signal at a second frequency f_(SOI). A CWlaser 102 generates a CW optical signal at an output that is connectedto an optical input of a Mach-Zehnder modulator 104. The modulator 104modulates the optical signal. An output of the Mach-Zehnder modulator104 is optically coupled to an optical link 106, which may be a singlemode fiber. A photodetector 108 is positioned along the optical link.The photodetector 108 generates an electrical current, I, at anelectrical output in response to the detected optical signal provided bythe link 106. To illustrate the operation, we assume the high-power andlow-power signals are represented by single frequency, continuous wavesine waves. The extension to finite bandwidth systems isstraightforward.

A large-signal model is used to predict the cancellation of a high-powersignal in the Mach-Zehnder modulator-based link architecture 100. TheMach-Zehnder modulator has an inherently sinusoidal transfer functionthat acts upon signals that themselves are sinusoidal waves. The resultis that the output fundamental signals and the distortion products arecharacterized by Bessel functions of the first kind. In conventionalphotonic links, that is, links that do not perform interference signalcancellation but that can use these same components, all parameters ofinterest are usually predicted using small-signal analysis, in which theBessel functions are approximated as finite series and only thelowest-order term or few terms are examined.

FIG. 1B illustrates a plot 130 showing the output signal power as afunction of input signal power for a fiber-optic link that uses theMach-Zehnder interferometric modulator link architecture of FIG. 1A. Theplot 130 illustrates the large-signal, Mach-Zehnder transfer functionthat shows the first two zeros 132, 134 of J₁(ϕ) which is thefirst-order Bessel function of the first kind, and in which ϕ is theangle modulation. Because of the modulator's sinusoidal transferfunction, the link's large-signal behavior can be described by Besselfunctions of the first kind. The link output is greatly suppressed atall input powers for which J₁(ϕ)=0. For the specific Mach-Zehndermodulator modeled here, the first two zeroes 132, 134 of J₁(ϕ) occur atinput powers of +13.3 dBm and +18.6 dBm.

FIG. 1C shows a graph 150 of the measured performance of a knowntechnique of suppression of RF interference. The graph 150 is based ondata from V. Urick, J. Diehl, J. McKinney, J. Singley, and C. Sunderman,“Nonlinear optical angle modulation for suppression of RF interference,”IEEE Trans. Microwave Theory Tech., vol. 64, ppl 2198-2204, July 2016.The graph 150 shows the measured performance of the technique describedin that paper. The graph 150 illustrates a plot of the output signalpower as a function of input signal power. The graph 150 shows theoutput of a link when two CW sine waves are input: the high- andlow-power input signals were supplied at frequencies f_(INT)=1,001 MHzand f_(SOI)=1,000 MHz, respectively. The low-power signal's input powerwas kept constant at −19 dBm while the high-power signal's input powerwas varied from −19 to +16 dBm. For a low-power signal at f_(SOI)=1,000MHz with a constant input power of −19 dBm and a high-power signal atf_(INT)=1,001 MHz with input power varying from −19 dBm to +16 dBm, themeasured output power at f_(SOI) f_(INT), and 2f_(INT)−f_(SOI)=1,002 MHzare plotted. The plots show that, at a high-power signal input power ofapproximately +13 dBm, the output power at f_(INT) is greatly suppressedbut the intermodulation distortion product at 2f_(INT)−f_(SOI) isexactly equal to the output power of the low-power signal at f_(SOI). Itcan be seen that when the input power of the high-power signal atf_(INT) is approximately +13 dBm, which for the modulator used in thisexperiment corresponded to the first zero of J₁(ϕ_(INT)), the outputpower at f_(INT) is suppressed by ˜60 dB. However, an additionalundesired term is generated at 2f_(INT)−f_(SOI)=1,002 MHz that has thesame output power as the desired, low-power signal at 1,000 MHz. In thisexample, where the signals are single frequency continuous wave sinewaves, it should be possible to filter out the undesired term. But, inan actual application, with “real” signals having a finite bandwidth,filtering would not be completely effective.

The methods and apparatus of the present teaching relate to thenonlinear function modification for interference suppression includingmitigation of intermodulation distortion. In particular, one feature ofthe methods and apparatus of the present teaching is that they canreduce or eliminate the undesirable intermodulation distortion productsignal term of the nonlinear processing described in connection withFIG. 1C. It should be understood that is possible to realize nonlinearfunction modification in either the analog domain or the digital domain.

Unlike known suppression techniques that involve using a small-signalmodel to derive the particular operating parameters, the presentteaching utilizes a large-signal model to derive the particularoperating parameters. The methods and apparatus of the present teachingare described in connection with a Mach-Zehnder interferometric opticalmodulator driven in a large signal mode of operation. However, the NLFMtechniques described herein are not limited to large-signal opticalmodulation. For example, NLFM can be applied to RF components, such asamplifiers using large-signal models appropriate for the transistorsused in the amplifier to derive the required operating parameters andthen modify the RF component's operation appropriately to achieve largesignal operation to suppress RF interfering signals while simultaneouslyreducing third-order intermodulation distortion products.

FIG. 2 illustrates an embodiment of a Mach-Zehnder modulator link 200using nonlinear function modification system of the present teaching. Inparticular, FIG. 2 illustrates an analog-domain implementation of theinterference suppression nonlinear function modification techniqueaccording to the present teaching. It should be understood the numbersshown in the link 200 are for illustrating one specific example and arenot meant to limit the teaching in any way.

Some known RF systems use two parallel Mach-Zehnder modulators toachieve linearization in an effort to extend the range of input signalpowers over which the generated distortion products remain below theoutput noise. However, these known RF systems rely on small signalmodulator operation. Subsystem settings necessary to achievelinearization can be derived from small-signal approximations of themodulator transfer function. One feature of the present teaching is therealization that the derivation of settings necessary to achievecancellation of both a high-power signal and the strongest third-orderintermodulation distortion products requires a large-signal model usingBessel functions of the first kind. This use of the large-signal modeland modulation with the nonlinear function modification described hereincan provide minimization of the interference signal at both theinterferer frequency and at the strongest third-order intermodulationdistortion frequencies. Furthermore, these features are provided withoutalso suppressing the signal of interest, which occurs with some knownhigh-power signal suppression approaches.

A first CW laser 202 includes an optical output that is coupled to anoptical input of a first Mach-Zehnder electro-optic modulator 204. Thefirst CW laser 202 generates an optical signal at a first wavelength,λ_(A). The output of the first modulator 204 is optically coupled to aninput of a wavelength division multiplexer 210 (or other opticalcombiner element). A second CW laser 206 includes an optical output thatis coupled to an optical input of a second Mach-Zehnder electro-opticmodulator 208. The second CW laser 206 generates an optical signal at asecond wavelength, λ_(B). However, it should be understood that in somemethods and apparatus according to the present teaching, a single laserwavelength can be used. That is, the first wavelength, λ_(A) can be thesame as the second wavelength, λ_(B). The output of the second modulator208 is optically coupled to another input of the wavelength divisionmultiplexer 210 (or other optical combiner element). The wavelengthdivision multiplexer 210 combines the optical signals at the twowavelengths, λ_(A), λ_(B) at an output.

The output of the wavelength division multiplexer 210 is opticallycoupled to an optical link 212. For example, the optical link 212 can bea single mode fiber optical link. An input of a photodetector 214 iscoupled to the optical link 212. The photodetector 214 provides acurrent, I, at an electrical output in response to the detected opticalsignal provided by the link 214. In cases of a single wavelength, otheroptical combiners can be used.

A driver circuit 216 includes electrical outputs that are connected tothe electrical modulation inputs of the first 204 and the secondMach-Zehnder electro-optic modulators 208. The driver circuit 216includes first and second signal generators 218, 220 that generate RFsignals at their respective outputs. In the experimental demonstrationshown, the first signal generator 218 is an RF interference signalgenerator and the second signal generator 220 generates the signal ofinterest. In practical implementations of the present teaching thesesignal generators can be one or more receiving antenna that receivesthese signals.

The respective outputs of the first 218 and second signal generators 220are coupled to respective inputs of the amplifier 222, 224. However, itshould be understood that some embodiments of the Mach-Zehnder modulatorlink 200 do not include these amplifiers 222, 224.

The outputs of the first 218 and second signal generators 220 areelectrically connected to inputs of respective ones of the first 226 andsecond electrical bandpass filters 228. However, it should be understoodthat some embodiments of the Mach-Zehnder modulator link 200 do notinclude these filters 226, 228. The filtered or unfiltered signals fromthe generators 218, 220 are combined in an electrical combiner 230. Forexample, the electrical combiner 230 can be a 3-dB combiner. The outputof the electrical combiner 230 is electrically connected to a 90° hybridcoupler 232 that produces so-called I and Q signals which are phaseshifted by 90° relative to one another. A first output 234 of the 90°hybrid coupler 232 is electrically connected to an electrical modulationinput of the first Mach-Zehnder electro-optic modulators 204 and asecond output 236 of the 90° hybrid coupler 232 is electricallyconnected to an electrical modulation input of the second Mach-Zehnderelectro-optic modulators 208. An attenuator 242 can be used to attenuatethe electrical modulation signal to the second Mach-Zehnderelectro-optic modulators 208.

In operation, the first and second CW laser 202, 206 generate first andsecond optical signals at the first and second wavelengths,respectively. The first optical signal at the first wavelengthpropagates to the optical input of the first Mach-Zehnder electro-opticmodulator 204 and the second optical signal at the second wavelengthpropagates to the optical input of the second Mach-Zehnder electro-opticmodulator 206.

The driver circuit 216 generates the first modulation signal thatmodulates the first optical signal at the first wavelength and generatesthe second modulation signal that modulates the second optical signal atthe second wavelength. The modulated first optical signal propagates tothe first input of the wavelength division multiplexer 210 and themodulated second optical signal propagates to the second input of thewavelength division multiplexer 210. The wavelength division multiplexer210 couples the multiplexed signal to the optical link 212. Thephotodetector 214 then generates an electrical current in response tothe multiplexed signal on the optical link.

The driver circuit 216 generates the first and second modulation signalsaccording to the present teaching so that the output power from thephotodetector 214 is minimized at both the interferer frequency and atthe strongest third-order intermodulation distortion frequencies withoutalso suppressing the signal of interest. More specifically, the firstand second signal generators 218, 220 generate RF signals at theirrespective outputs that can be amplified by their respective amplifier222, 224. The resulting signals are filtered by respective ones of thefirst and second electrical bandpass filters 226, 228 and then combinedby the combiner 230. The combined signal is then fed to the 90° hybridcoupler 232 that produces the I and Q signals that are phase shifted by90° relative to one another. The function of the 90° hybrid coupler 232is to split the signal and provide the desired relative phase shift. Itshould be understood that other splitter components can be used, forexample, various directional coupler components can be used.

In one method of operation according to the present teaching, thevarious components of the driver 216 are configured and operated so thatthe input signal at the interferer frequency, f_(INT), is made tomodulate the first Mach-Zehnder modulator 204 at one of the zeroes ofJ₁(ϕ_(INT)). The second Mach-Zehnder modulator 208 enables the nonlinearfunction modification. When the interferer signal's power causes thephase modulation in the arms of the modulator's 204 interferometer tocorrespond to the second zero of J₁(ϕ_(INT)), which occurs atϕ_(INT)=7.0156, the RF attenuator 242 shown in FIG. 2 ensures that thissame interferer signal power also corresponds to ϕ_(INT)=3.8317 at thesecond modulator 208, which is the first zero of J₁(ϕ_(INT)). Definingr_(I) as the ratio of DC photocurrent imposed by the laser 206 atwavelength λ_(B) to the DC photocurrent I_(dc,A) imposed by the laser204 at wavelength λ_(A), the output photocurrent at the interferer,signal-of-interest, and third-order intermodulation distortionfrequencies f_(INT), f_(SOI), and 2f_(INT)±f_(SOI), respectively, are asfollows when one modulator is biased at a quadrature bias on a positiveslope of its transfer function and the other at quadrature on a negativeslope:

     I(f_(INT)) = I_(dc, A)J₀(ϕ_(SOI))[J₁(3.8317) − jr_(I)J₁(7.0156)]$\mspace{79mu}{{I\left( f_{SOI} \right)} \cong {I_{{dc},A}{{J_{1}\left( \phi_{SOI} \right)}\left\lbrack {{J_{0}(3.8317)} - {j\frac{7.0156}{3.8317}r_{I}{J_{0}(7.0156)}}} \right\rbrack}}}$  and${I\left( {{2f_{INT}} \pm f_{SOI}} \right)} \cong {{- I_{{dc},A}}{{{J_{1}\left( \phi_{SOI} \right)}\left\lbrack {{J_{2}(3.8317)} + {\frac{7.0156}{3.8317}r_{I}{J_{2}(7.0156)}}} \right\rbrack}.}}$When the ratio of laser output powers is adjusted so that r_(I)=0.7331,these equations reduce toI(f _(INT))=0I(f _(SOI))≅−0.4028[1+j]J ₁(ϕ_(SOI))I _(dc,A)≠0andI(2f _(INT) ±f _(SOI))≅0.

Therefore, output power from the photodetector 214 is minimized at boththe interferer frequency and at the strongest third-orderintermodulation distortion frequencies without also suppressing thesignal of interest. Such a result would not have been possible using thepreviously demonstrated single-modulator architecture. Thus, FIG. 2illustrates application of nonlinear function modification that enablessuppression of a high-power interferer at frequency I_(INT) and recoversa lower-power signal of interest at frequency f_(SOI) without generatingan equally strong third-order intermodulation distortion product atfrequencies 2f_(INT)±f_(SOI).

It should be understood that there are many different configurationsthat can be used to practice the present teaching. For example, invarious embodiments, one or both of the generators 218, 220, one or bothof the amplifiers 222, 224, one or both of the bandpass filters 226, 228and/or the combiner 230 may not be included. In some embodiments, asignal comprising a low-power signal of interest and an interferingsignal may be provided directly to a splitter (e.g. 90° hybrid coupler232). Also, in some embodiments, an antenna is connected to the splitter(e.g. 90° hybrid coupler 232) to provide the RF signal.

An experiment was performed to confirm that the architecture in FIG. 2successfully recovers a low-power signal of interest while suppressing ahigh-power interferer and the strong third-order intermodulationdistortion product generated by known techniques. In this experiment,the high- and low-power input signals were supplied at frequenciesf_(INT)=500 MHz from generator 218 and f_(SOI)=200 MHz from the othergenerator 220. The arrangement of the directional coupler 232 and RFattenuator 242 shown in FIG. 2 caused the input signals at f_(INT) andf_(SOI) to be imposed at the input to one of the two modulators 204 at apower ˜5 dB higher than at the input to the other modulator 208, suchthat a high-power signal input power existed that corresponded to thefirst two zeros of J₁(ϕ).

In general, this analog-domain implementation of nonlinear functionmodification requires that light in two optical paths be modulatedseparately and combined onto a single photodetector. Optical combinationof the two modulated optical carriers can be carried out mostefficiently when a commercially available wavelength-divisionmultiplexer (WDM) is used to incoherently combine light of two differentwavelengths. In the specific implementation shown in FIG. 2, laser A 202and laser B 206 supplied optical carriers at wavelengths λ_(A) and λ_(B)differing in frequency by 200 GHz with powers that induced DCphotocurrents at quadrature of 4.5 mA and 3.3 mA, respectively, suchthat the ratio r_(I) was ˜0.73. The above equations show that this setof operating conditions should result in suppression of the outputsignals at both f_(INT)=500 MHz and 2f_(INT)−f_(SOI)=800 MHz withoutsignificantly suppressing the signal of interest at f_(SOI)=200 MHz.

FIG. 3 illustrates a graph 300 showing measured results from theexperiment to verify the nonlinear function modification capability ofthe architecture described in connection with FIG. 2. For a low-powersignal at f_(SOI)=200 MHz with a constant input power of −10 dBm and ahigh-power signal at f_(INT)=500 MHz with input power varying from +6.5dBm to +30 dBm, the measured output power at, f_(SOI) f_(INT), and2f_(INT)−f_(SOI)=800 MHz are plotted, showing that, for a high-powerinput signal power of +28.5 dBm, both the high-power signal at f_(INT),and the intermodulation distortion product at 2f_(INT)−f_(SOI) aregreatly suppressed while preserving the low-power signal at f_(SOI).

In particular, the graph 300 of FIG. 3 shows the output signals measuredon an RF spectrum analyzer under the above conditions. For a low-powersignal at f_(SOI)=200 MHz with a constant input power of −10 dBm and ahigh-power signal at f_(INT)=500 MHz with input power varying from +6.5dBm to +30 dBm, the measured output power at, f_(SOI) f_(INT), and2f_(INT)−f_(SOI)=800 MHz are plotted, showing that, for a high-powerinput signal power of +28.5 dBm, both the high-power signal at f_(INT),and the intermodulation distortion product at 2f_(INT)−f_(SOI) aregreatly suppressed while preserving the low-power signal at f_(SOI).Compared to the results obtained using the known techniques asillustrated in FIG. 1, the measured results illustrated in FIG. 3 showsuppression of the high-power signal to the same degree as had beenachieved using the single modulator technique, but also show suppressionof the third-order intermodulation distortion product by approximately30 dB relative to what was achieved in the prior art technique. Thelow-power signal of interest, meanwhile, is not suppressed, and thisshows that nonlinear function modification has been successfullyrealized to accomplish the interference suppression objective that canbe achieved by the present teaching.

If both modulators were biased exactly at quadrature points and therewere no other contributions to 2nd-order distortion, the outputs at2f_(SOI) and f_(INT)±f_(SOI) would ostensibly be zero. Therefore all ofthe most problematic intermodulation distortion products and the secondharmonic of the high-power signal are all suppressed while preservingthe low-power signal of interest.

Thus, the method and apparatus of the present teaching overcomes thedeficiencies of known methods and systems in performing interferencesuppression with intermodulation distortion mitigation. An RF signalcomprising an RF signal of interest and an RF interfering signal isprocessed to produce a first and second RF drive signal, each with adesired RF interfering signal power and having a 90 degree relativephase. For example, the processing can be attenuating, amplifying,and/or filtering. In many systems, the desired RF interfering signalpower can be adjusted so that the third-order intermodulation distortionproducts remain below a predetermined noise level.

The first RF drive signal is imposed or modulated onto a first opticalsignal with an optical modulator having a sinusoidal transfer functionand biased at quadrature with a first slope, thereby generating a firstmodulated optical signal. The first RF drive signal with the desired RFinterfering signal power causes the modulator to have a large-signalbehavior that is characterized by a Bessel function of the first kindJ1(ϕ), wherein the desired RF interfering signal power of the firstdrive signal is chosen to correspond to a zero of the Bessel function ofthe first kind J1(ϕ). Similarly, the second RF drive signal is imposedor modulated onto a second optical signal with an optical modulatorhaving a sinusoidal transfer function and biased at quadrature with asecond slope having a direction that is opposite to a direction of thefirst slope, thereby generating a second modulated optical signal. Thefirst and second optical frequency can be the same or different opticalfrequencies. The second RF drive signal with the desired RF interferingsignal power causes the modulator to have a large-signal behavior thatis characterized by a Bessel function of the first kind J1(ϕ), whereinthe desired power at a frequency of the interference signal of thesecond drive signal is chosen to correspond to another zero of theBessel function of the first kind J1(ϕ). The first and second modulatedoptical signal are combined with an optical power ratio that is selectedto suppress third-order intermodulation distortion products in anelectrical signal generated by detecting the optically combined firstand second modulated optical signals.

EQUIVALENTS

While the Applicant's teaching is described in conjunction with variousembodiments, it is not intended that the Applicant's teaching be limitedto such embodiments. On the contrary, the Applicant's teachingencompasses various alternatives, modifications, and equivalents, aswill be appreciated by those of skill in the art, which may be madetherein without departing from the spirit and scope of the teaching.

What is claimed is:
 1. A method of interference suppression withintermodulation distortion mitigation, the method comprising: a)processing an RF signal comprising an RF signal of interest and an RFinterfering signal to produce a first and second RF drive signal eachwith a desired RF interfering signal power and having a 90 degreerelative phase; b) imposing the first RF drive signal onto a firstoptical signal with an optical modulator having a sinusoidal transferfunction and biased at quadrature with a first slope, thereby generatinga first modulated optical signal, the first RF drive signal with thedesired RF interfering signal power causing the modulator to have alarge-signal behavior that is characterized by a Bessel function of thefirst kind J₁(ϕ), wherein the desired RF interfering signal power of thefirst drive signal is chosen to correspond to a zero of the Besselfunction of the first kind J₁(ϕ); c) imposing the second RF drive signalonto a second optical signal with an optical modulator having asinusoidal transfer function and biased at quadrature with a secondslope having a direction that is opposite to a direction of the firstslope, thereby generating a second modulated optical signal, the secondRF drive signal with the desired RF interfering signal power causing themodulator to have a large-signal behavior that is characterized by aBessel function of the first kind J₁(ϕ), wherein the desired power at afrequency of the interference signal of the second drive signal ischosen to correspond to another zero of the Bessel function of the firstkind J₁(ϕ); and d) optically combining the first and second modulatedoptical signal with an optical power ratio that is selected to suppressthird-order intermodulation distortion products in an electrical signalgenerated by detecting the optically combined first and second modulatedoptical signals.
 2. The method of claim 1 wherein the processingcomprises attenuating the RF signal.
 3. The method of claim 1 whereinthe processing comprises amplifying the RF signal.
 4. The method ofclaim 1 wherein the processing comprises filtering the RF signal.
 5. Themethod of claim 4 wherein the filtering comprises bandpass filtering. 6.The method of claim 1 wherein the first optical signal is at a firstwavelength and the second optical signal is at a second wavelength. 7.The method of claim 1 wherein the first wavelength and the secondwavelength are the same wavelength.
 8. The method of claim 1 wherein theoptical modulators having the sinusoidal transfer function areMach-Zehnder interferometric modulators.
 9. The method of claim 1further comprising adjusting the desired RF interfering signal power ofthe first and second drive signals so that the third-orderintermodulation distortion products remain below a predetermined noiselevel.
 10. The method of claim 1 further comprising detecting theoptically combined first and second modulated optical signals andgenerating the electrical signal.
 11. A method of interferencesuppression with intermodulation distortion mitigation, the methodcomprising: a) processing an RF signal comprising an RF signal ofinterest and an RF interfering signal; b) splitting and phase shiftingthe processed RF signal to produce a first and second RF drive signalthat are phase shifted by 90° relative to one another; c) attenuating atleast one of the first and second RF drive signals to provide a first RFdrive signal with a desired RF interfering signal power and a second RFdrive signal with a desired RF interfering signal power; d) modulating afirst optical signal with the first RF drive signal using a firstoptical interferometric modulator with a sinusoidal transfer functionbiased at quadrature with a first slope, the first RF drive signal withthe desired RF interfering signal power causing the first opticalinterferometric modulator to have a large-signal behavior that ischaracterized by a Bessel function of the first kind J₁(ϕ), wherein thedesired RF interfering signal power at a frequency of the interferencesignal of the first drive signal is chosen to correspond to a zero ofthe Bessel function of the first kind J₁(ϕ); e) modulating a secondoptical signal with the second RF drive signal using a second opticalinterferometric modulator with a sinusoidal transfer function biased atquadrature with a second slope having a direction that is opposite to adirection of the first slope, the second RF drive signal with thedesired RF interfering signal power causing the second opticalinterferometric modulator to have a large-signal behavior that ischaracterized by a Bessel function of the first kind J₁(ϕ), wherein thedesired power at a frequency of the interference signal of the seconddrive signal is chosen to correspond to another zero of the Besselfunction of the first kind J₁(ϕ); f) combining the first and secondmodulated optical signal; and g) detecting the combined first and secondmodulated optical signals to generate an electrical signal, wherein thecombining the first and second modulated optical signal is performedwith an optical power ratio such that the electrical signal representsthe RF signal of interest with the RF interfering signal suppressed andthird-order intermodulation distortion products reduced.
 12. The methodof claim 11 wherein the processing the RF signal comprises filtering theRF signal.
 13. The method of claim 12 wherein the filtering the RFsignal comprises bandpass filtering the RF signal.
 14. The method ofclaim 11 wherein the processing the RF signal comprises amplifying theRF signal.
 15. The method of claim 11 wherein the processing the RFsignal comprises attenuating the RF signal.
 16. The method of claim 11wherein at least one of the first and second interferometric modulatorscomprises a Mach-Zehnder modulator.
 17. An interference suppression withintermodulation distortion mitigation system, the system comprising: a)an electrical input that receives an RF signal comprising an RF signalof interest and an RF interfering signal; b) an electrical splitter andattenuator having an input that is coupled to the electrical input, theelectrical splitter and attenuator splitting the electrical input signalinto an I signal at a first output and a Q-signal at a second output,wherein the I-signal and the Q-signal are phase shifted by 90° relativeto one another and at least one of the I-signal and the Q-signal areattenuated; c) a first optical interferometric modulator with asinusoidal transfer function biased at quadrature with a first slope,the first optical interferometric modulator having an optical inputcoupled to an output of a first laser that generates a first opticalsignal at a first wavelength and having an electrical input that iselectrically coupled to the first output of the electrical splitter andattenuator, the first optical interferometric modulator generating afirst modulated optical signal corresponding to a Bessel function of thefirst kind J₁(ϕ) driven to a zero; d) a second optical interferometricmodulator with a sinusoidal transfer function biased at quadrature witha second slope having a direction that is opposite to a direction of thefirst slope, the second optical interferometric modulator having anoptical input that coupled to an output of a second laser that generatesa second optical signal at a second wavelength and having an electricalinput that is electrically coupled to the second output of theelectrical splitter and attenuator, the second optical interferometricmodulator generating a second modulated optical signal corresponding toa Bessel function of the first kind J₁(ϕ) driven to another zero; e) anoptical combiner that combines the first and second modulated opticalsignal; and f) an optical detector that detects the combined first andsecond modulated optical signals to generate an electrical signal,wherein the optical combiner combines the first and second modulatedoptical signal with an optical power ratio such that the electricalsignal represents the signal of interest with the RF interfering signalsuppressed and third-order intermodulation distortion products reduced.18. The system of claim 17 wherein the electrical input is a singleantenna.
 19. The system of claim 17 wherein at least one of the firstand second optical interferometric modulators is a Mach-Zehnderinterferometric modulator.
 20. The system of claim 17 wherein theelectrical splitter and attenuator comprises a 90 degree hybrid coupler.